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| lt1996 1 1996f resistor matching (%) percentage of units (%) 0.04 1996 ta01b C 0.02 0 0.02 40 35 30 25 20 15 10 5 0 C 0.04 lt1996a g = 81 typical applicatio u features pin configurable as a difference amplifier, inverting and noninverting amplifier difference amplifier gain range 9 to 117 cmrr >80db noninverting amplifier gain range 0.008 to 118 inverting amplifier gain range C0.08 to C117 gain error: <0.05% gain drift: < 3ppm/ c wide supply range: single 2.7v to split 18v micropower operation: 100 a supply input offset voltage: 50 v (max) gain bandwidth product: 560khz rail-to-rail output space saving 10-lead msop and dfn packages precision, 100 a gain selectable amplifier the lt ? 1996 combines a precision operational amplifier with eight precision resistors to form a one-chip solution for accurately amplifying voltages. gains from C117 to 118 with a gain accuracy of 0.05% can be achieved without any external components. the device is particularly well suited for use as a difference amplifier, where the excellent resistor matching results in a common mode rejection ratio of greater than 80db. the amplifier features a 50 v maximum input offset voltage and a gain bandwidth product of 560khz. the device operates from any supply voltage from 2.7v to 36v and draws only 100 a supply current on a 5v supply. the output swings to within 40mv of either supply rail. the internal resistors have excellent matching character- istics; variation is 0.05% over temperature with a guaran- teed matching temperature coefficent of less than 3ppm/ c. the resistors are also extremely stable over voltage, exhibiting a nonlinearity of less than 10ppm. the lt1996 is fully specified at 5v and 15v supplies and from C40 c to 85 c. the device is available in space saving 10-lead msop and dfn packages. for an amplifier with selectable gains from C13 to 14, see the lt1991 data sheet. descriptio u applicatio s u rail-to-rail gain = 9 difference amplifier distribution of resistor matching C + 15v C15v ? v in v m(in) v p(in) C + v out = v ref + 9 ? ? v in swing 40mv to either rail input range 60v r in = 100k ? lt1996 1996 ta01 450k/81 450k/81 450k/27 450k/27 450k/9 450k 450k 450k/9 4pf 4pf v ref , ltc and lt are registered trademarks of linear technology corporation. all other trademarks are the property of their respective owners. patents pending. handheld instrumentation medical instrumentation strain gauge amplifiers differential to single-ended conversion
lt1996 2 1996f symbol parameter conditions min typ max units ? g gain error v s = 15v, v out = 10v; r l = 10k g = 81; lt1996ams 0.02 0.05 % g = 27; lt1996ams 0.03 0.06 % g = 9; lt1996ams 0.03 0.07 % g = 81; lt1996add 0.02 0.05 % g = 27; lt1996add 0.02 0.07 % g = 9; lt1996add 0.03 0.08 % g = 81; lt1996 0.04 0.12 % g = 27; lt1996 0.04 0.12 % g = 9; lt1996 0.04 0.12 % gnl gain nonlinearity v s = 15v; v out = 10v; r l = 10k; g = 9 1 10 ppm ? g/ ? t gain drift vs temperature (note 6) v s = 15v; v out = 10v; r l = 10k 0.3 3 ppm/ c cmrr common mode rejection ratio, v s = 15v; g = 9; v cm = 15.3v referred to inputs (rti) lt1996ams 80 100 db lt1996add 80 100 db lt1996 70 100 db v s = 15v; g = 27; v cm = C14.5v to 14.3v lt1996ams 95 105 db lt1996add 90 105 db lt1996 75 105 db package/order i for atio uu w total supply voltage (v + to v C ) ............................... 40v input voltage (pins p9/m9, note 2) ....................... 60v input current (pins p27/m27/p81/m81, note 2) .................. 10ma output short-circuit duration (note 3) ............ indefinite operating temperature range (note 4) ...C40 c to 85 c specified temperature range (note 5) ....C40 c to 85 c order part number ms part marking* t jmax = 150 c, ja = 230 c/w ltbpb lt1996cms lt1996ims lt1996acms lt1996aims absolute axi u rati gs w ww u (note 1) the denotes the specifications which apply over the full operating temperature range, otherwise specifications are at t a = 25 c. difference amplifier configuration, v s = 5v, 0v or 15v; v cm = v ref = half supply, unless otherwise noted. *temperature and electrical grades are identified by a label on the shipping container. c onsult ltc marketing for parts specified with wider operating temperature ranges. 1 2 3 4 5 p9 p27 p81 v ee ref 10 9 8 7 6 m9 m27 m81 v cc out top view ms package 10-lead plastic msop maximum junction temperature dd package ...................................................... 125 c ms package ..................................................... 150 c storage temperature range dd package .......................................C65 c to 125 c ms package ......................................C65 c to 150 c msopClead temperature (soldering, 10 sec)...... 300 c order part number dd part marking* t jmax = 125 c, ja = 160 c/w underside metal connected to v ee (pcb connection optional) LBPC lt1996cdd lt1996idd lt1996acdd lt1996aidd top view dd package 10-lead (3mm 3mm) plastic dfn 10 9 6 7 8 4 5 3 2 1 m9 m27 m81 v cc out p9 p27 p81 v ee ref electrical characteristics lt1996 3 1996f symbol parameter conditions min typ max units cmrr common mode rejection ratio (rti) v s = 15v; g = 81; v cm = C14.1v to 13.9v lt1996ams 105 120 db lt1996add 100 120 db lt1996 85 120 db v cm input voltage range (note 7) p9/m9 inputs v s = 15v; v ref = 0v C15.5 15.3 v v s = 5v, 0v; v ref = 2.5v 0.84 3.94 v v s = 3v, 0v; v ref = 1.25v 0.98 1.86 v p9/m9 inputs, p81/m81 connected to ref v s = 15v; v ref = 0v C60 60 v v s = 5v, 0v; v ref = 2.5v C12.6 15.6 v v s = 3v, 0v; v ref = 1.25v C1.25 6.8 v p27/m27 inputs v s = 15v; v ref = 0v C14.5 14.3 v v s = 5v, 0v; v ref = 2.5v 0.95 3.84 v v s = 3v, 0v; v ref = 1.25v 1 1.82 v p81/m81 inputs v s = 15v; v ref = 0v C14.1 13.9 v v s = 5v, 0v; v ref = 2.5v 0.99 3.81 v v s = 3v, 0v; v ref = 1.25v 1 1.8 v v os op amp offset voltage (note 8) lt1996ams, v s = 5v, 0v 15 50 v 135 v lt1996ams, v s = 15v 15 80 v 160 v lt1996ms 25 100 v 200 v lt1996dd 25 150 v 250 v ? v os / ? t op amp offset voltage drift (note 6) 0.3 1 v/ c i b op amp input bias current 2.5 5 na 7.5 na i os op amp input offset current lt1996a 50 500 pa 750 pa lt1996 50 1000 pa 1500 pa op amp input noise voltage 0.01hz to 1hz 0.35 v p-p 0.01hz to 1hz 0.07 v rms 0.1hz to 10hz 0.25 v p-p 0.1hz to 10hz 0.05 v rms e n input noise voltage density g = 9; f = 1khz 46 nv/ hz (includes resistor noise) g = 117; f = 1khz 18 nv/ hz r in input impedance (note 10) p9 (m9 = ground) 350 500 650 k ? p27 (m27 = ground) 326.9 467 607.1 k ? p81 (m81 = ground) 319.2 456 592.8 k ? m9 (p9 = ground) 35 50 65 k ? m27 (p27 = ground) 11.69 16.7 21.71 k ? m81 (p81 = ground) 3.85 5.5 7.15 k ? the denotes the specifications which apply over the full operating temperature range, otherwise specifications are at t a = 25 c. difference amplifier configuration, v s = 5v, 0v or 15v; v cm = v ref = half supply, unless otherwise noted. electrical characteristics lt1996 4 1996f symbol parameter conditions min typ max units ? r resistor matching (note 9) g = 81; lt1996ams 0.02 0.05 % g = 27; lt1996ams 0.03 0.06 % g = 9; lt1996ams 0.03 0.07 % g = 81; lt1996add 0.02 0.05 % g = 27; lt1996add 0.02 0.07 % g = 9; lt1996add 0.03 0.08 % g = 81; lt1996 0.04 0.12 % g = 27; lt1996 0.04 0.12 % g = 9; lt1996 0.04 0.12 % ? r/ ? t resistor temperature coefficient (note 6) resistor matching 0.3 3 ppm/ c absolute value C30 ppm/ c psrr power supply rejection ratio v s = 1.35v to 18v (note 8) 105 135 db minimum supply voltage 2.4 2.7 v v out output voltage swing (to either rail) no load v s = 5v, 0v 40 55 mv v s = 5v, 0v 65 mv v s = 15v 110 mv 1ma load v s = 5v, 0v 150 225 mv v s = 5v, 0v 275 mv v s = 15v 300 mv i sc output short-circuit current (sourcing) drive output positive; 8 12 ma short output to ground 4ma output short-circuit current (sinking) drive output negative; 8 21 ma short output to v s or midsupply 4ma bw C3db bandwidth g = 9 38 khz g = 27 17 khz g = 81 7 khz gbwp op amp gain bandwidth product f = 10khz 560 khz t r , t f rise time, fall time g = 9; 0.1v step; 10% to 90% 8 s g = 81; 0.1v step; 10% to 90% 40 s t s settling time to 0.01% g = 9; v s = 5v, 0v; 2v step 85 s g = 9; v s = 5v, 0v; C2v step 85 s g = 9; v s = 15v; 10v step 110 s g = 9; v s = 15v; C10v step 110 s sr slew rate v s = 5v, 0v; v out = 1v to 4v 0.06 0.12 v/ s v s = 15v; v out = 10v 0.08 0.12 v/ s i s supply current v s = 5v, 0v 100 110 a 150 a v s = 15v 130 160 a 210 a note 1: absolute maximum ratings are those beyond which the life of the device may be impaired. note 2: the p27/m27 and p81/m81 inputs are protected by esd diodes to the supply rails. if one of these four inputs goes outside the rails, the input current should be limited to less than 10ma. the p9/m9 inputs can withstand 60v if p81/m81 are grounded and v s = 15v (see applications information section about high voltage cm difference amplifiers). note 3: a heat sink may be required to keep the junction temperature below absolute maximum ratings. the denotes the specifications which apply over the full operating temperature range, otherwise specifications are at t a = 25 c. difference amplifier configuration, v s = 5v, 0v or 15v; v cm = v ref = half supply, unless otherwise noted. electrical characteristics lt1996 5 1996f supply current vs supply voltage output voltage swing vs temperature output voltage swing vs load current (output low) output voltage swing vs load current (output high) output short-circuit current vs temperature input offset voltage vs difference gain typical perfor a ce characteristics uw (difference amplifier configuration) note 4: both the lt1996c and lt1996i are guaranteed functional over the C40 c to 85 c temperature range. note 5: the lt1996c is guaranteed to meet the specified performance from 0 c to 70 c and is designed, characterized and expected to meet specified performance from C40 c to 85 c but is not tested or qa sampled at these temperatures. the lt1996i is guaranteed to meet specified performance from C40 c to 85 c. note 6: this parameter is not 100% tested. note 7: input voltage range is guaranteed by the cmrr test at v s = 15v. for the other voltages, this parameter is guaranteed by design and through correlation with the 15v test. see the applications information section to determine the valid input voltage range under various operating conditions. note 8: offset voltage, offset voltage drift and psrr are defined as referred to the internal op amp. you can calculate output offset as follows. in the case of balanced source resistance, v os, out = v os ? noise gain + i os ? 450k + i b ? 450k ? (1 C r p /r n ) where r p and r n are the total resistance at the op amp positive and negative terminal respectively. note 9: resistors connected to the minus inputs. resistor matching is not tested directly, but is guaranteed by the gain error test. note 10: input impedance is tested by a combination of direct measurements and correlation to the cmrr and gain error tests. supply voltage ( v) 0 supply current ( a) 200 175 150 125 100 75 50 25 0 16 1996 g01 4 2 6 10 14 18 8 12 20 t a = 85 c t a = C40 c t a = 25 c load current (ma) 0 output voltage (mv) 1400 1200 1000 800 600 400 200 v ee 1996 g03 2 10 9 8 7 6 5 1 34 v s = 5v, 0v t a = 85 c t a = C40 c t a = 25 c load current (ma) v cc C100 C200 C300 C400 C500 C600 C700 C800 C900 C1000 output voltage swing (mv) 1996 g04 0123 4 5 67 8910 v s = 5v, 0v t a = 85 c t a = C40 c t a = 25 c temperature ( c) C50 output short-circuit current (ma) 25 20 15 10 5 0 0 50 75 1996 g05 C25 25 100 125 v s = 5v, 0v sinking sourcing gain (v/v) 9 input offset voltage ( v) 150 100 50 0 C50 C100 C150 108 81 90 99 117 45 1996 g06 18 27 72 63 54 36 v s = 5v, 0v representative parts temperature ( c) C50 output voltage swing (mv) 100 1996 g02 050 60 40 20 v ee C25 25 75 125 v s = 5v, 0v no load output high (right axis) output low (left axis) v cc C20 C40 C60 electrical characteristics lt1996 6 1996f typical perfor a ce characteristics uw (difference amplifier configuration) output impedance vs frequency cmrr vs temperature gain error vs temperature bandwidth vs gain cmrr vs frequency psrr vs frequency output offset voltage vs difference gain gain error vs load current slew rate vs temperature gain (v/v) 9 output offset voltage (mv) 10.0 7.5 5.0 2.5 0 C2.5 C5.0 C7.5 C10.0 108 81 90 99 117 45 1996 g07 18 27 72 63 54 36 v s = 5v, 0v representative parts load current (ma) 0 gain error (%) 3 5 1996 g08 12 4 0.04 0.03 0.02 0.01 0 C0.01 C0.02 C0.03 C0.04 gain = 81 v s = 15v v out = 10v t a = 25 c representative units temperature ( c) C50 slew rate (v/ s) 0.30 0.25 0.20 0.15 0.10 0.05 0 25 75 1996 g09 C25 0 50 100 125 gain = 9 v s = 15v v out = 10v sr C (falling edge) sr + (rising edge) gain (v/v) 9 C3db bandwidth (khz) 40 35 30 25 20 15 10 5 0 27 45 63 81 1996 g10 99 117 18 36 54 72 90 108 v s = 5v, 0v t a = 25 c frequency (hz) cmrr (db) 130 120 110 100 90 80 70 60 50 40 30 20 10 0 10 1k 10k 1m 1996 g11 100 100k v s = 5v, 0v t a = 25 c gain = 9 gain = 27 gain = 81 psrr (db) 120 110 100 90 80 70 60 50 40 30 20 10 0 v s = 5v, 0v t a = 25 c gain = 9 gain = 27 frequency (hz) 10 1k 10k 1996 g12 100 100k gain = 81 frequency (hz) output impedance ( ? ) 1 100 1k 100k 10k 1996 g13 10 1000 100 10 1 0.1 0.01 v s = 5v, 0v t a = 25 c gain = 9 gain = 27 gain = 81 temperature ( c) C50 cmrr (db) 120 100 80 60 40 20 0 25 75 1996 g14 C25 0 50 100 125 gain = 9 v s = 15v representative units temperature ( c) C50 gain error (%) 0.030 0.025 0.020 0.015 0.010 0.005 0 25 75 1996 g15 C25 0 50 100 125 gain = 9 v s = 15v representative units lt1996 7 1996f uu u pi fu ctio s p9 (pin 1): noninverting gain-of-9 input. connects a 50k internal resistor to the op amps noninverting input. p27 (pin 2): noninverting gain-of-27 input. connects a (50k/3) internal resistor to the op amps noninverting input. p81 (pin 3): noninverting gain-of-81 input. connects a (50k/9) internal resistor to the op amps noninverting input. v ee (pin 4): negative power supply. can be either ground (in single supply applications), or a negative voltage (in split supply applications). ref (pin 5): reference input. sets the output level when difference between inputs is zero. connects a 450k internal resistor to the op amps noninverting input. out (pin 6): output. v out = v ref + 9 ? (v p1 C v m1 ) + 27 ? (v p3 C v m3 ) + 81 ? (v p9 C v m9 ). v cc (pin 7): positive power supply. can be anything from 2.7v to 36v above the v ee voltage. m81 (pin 8): inverting gain-of-81 input. connects a (50k/9) internal resistor to the op amps inverting input. m27 (pin 9): inverting gain-of-27 input. connects a (50k/3) internal resistor to the op amps inverting input. m9 (pin 10): inverting gain-of-9 input. connects a 50k internal resistor to the op amps inverting input. (difference amplifier configuration) gain and phase vs frequency gain vs frequency small signal transient response, gain = 9 small signal transient response, gain = 27 0.01hz to 1hz voltage noise typical perfor a ce characteristics uw (difference amplifier configuration) frequency (khz) gain (db) 1996 g16 v s = 5v, 0v t a = 25 c 50 40 30 20 10 0 0.5 10 100 500 1 gain = 9 gain = 27 gain = 81 frequency (khz) 1 gain (db) phase (deg) 10 100 400 1996 g17 0.1 v s = 5v, 0v t a = 25 c gain = 9 phase (right axis) gain (left axis) 0 C20 C40 C60 C80 C100 C120 C140 C160 C180 C200 40 30 20 10 C10 0 v s = 15v t a = 25 c measured in g =117 referred to op amp inputs 0 10 2030405060708090100 time (s) op amp voltage noise (100nv/div) 1996 g21 50mv/div 10 s/div 1996 g18 50mv/div 20 s/div 1996 g19 50mv/div 50 s/div 1996 g20 small signal transient response, gain = 81 lt1996 8 1996f introduction the lt1996 may be the last op amp you ever have to stock. because it provides you with several precision matched resistors, you can easily configure it into several different classical gain circuits without adding external compo- nents. the several pages of simple circuits in this data sheet demonstrate just how easy the lt1996 is to use. it can be configured into difference amplifiers, as well as into inverting and noninverting single ended amplifiers. the fact that the resistors and op amp are provided together in such a small package will often save you board space and reduce complexity for easy probing. the op amp the op amp internal to the lt1996 is a precision device with 15 v typical offset voltage and 3na input bias cur- rent. the input offset current is extremely low, so match- ing the source resistance seen by the op amp inputs will provide for the best output accuracy. the op amp inputs are not rail-to-rail, but extend to within 1.2v of v cc and 1v of v ee . for many configurations though, the chip inputs will function rail-to-rail because of effective attenuation to the +input. the output is truly rail-to-rail, getting to within 40mv of the supply rails. the gain bandwidth product of the op amp is about 560khz. in noise gains of 2 or more, it is stable into capacitive loads up to 500pf. in noise gains below 2, it is stable into capacitive loads up to 100pf. the resistors the resistors internal to the lt1996 are very well matched sichrome based elements protected with barrier metal. although their absolute tolerance is fairly poor ( 30%), their matching is to within 0.05%. this allows the chip to achieve a cmrr of 80db, and gain errors within 0.05%. the resistor values are (450k/9), (450k/27), (450k/81) and 450k, connected to each of the inputs. the resistors have power limitations of 1watt for the 450k and (450k/81) resistors, 0.3watt for the (450k/27) resistors and 0.5watt for the (450k/9) resistors; however, in practice, power dissipation will be limited well below these values by the block diagra w lt1996 1996 bd 9 8 2 3 4 5 7 6 10 1 m9 m27 m81 p9 p27 p81 v cc v ee out ref 450k/81 450k/27 450k/27 450k/9 450k/9 450k 4pf 450k 450k/81 4pf + C out applicatio s i for atio wu u u lt1996 9 1996f maximum voltage allowed on the input and ref pins. the 50k resistors connected to the m9 and p9 inputs are isolated from the substrate, and can therefore be taken beyond the supply voltages. the naming of the pins p9, p27, p81, etc., is based on their admittances relative to the feedback and ref admittances. because it has 9 times the admittance, the voltage applied to the p9 input has 9 times the effect of the voltage applied to the ref input. bandwidth the bandwidth of the lt1996 will depend on the gain you select (or more accurately the noise gain resulting from the gain you select). in the lowest configurable gain of 1, the C3db bandwidth is limited to 450khz, with peaking of about 2db at 280khz. in the highest configurable gains, bandwidth is limited to 5khz. input noise the lt1996 input noise is comprised of the johnson noise of the internal resistors ( 4ktr), and the input voltage noise of the op amp. paralleling all four resistors to the +input gives a 3.8k ? resistance, for 8nv/ hz of voltage noise. the equivalent network on the Cinput gives another 8nv/ hz, and the op amp 14nv/ hz. taking their rms sum gives a total 18nv/ hz input referred noise floor. output noise depends on configuration and noise gain. input resistance the lt1996 input resistances vary with configuration, but once configured are apparent on inspection. note that resistors connected to the op amps Cinput are looking into a virtual ground, so they simply parallel. any feedback resistance around the op amp does not contribute to input resistance. resistors connected to the op amps +input are looking into a high impedance, so they add as parallel or series depending on how they are connected, and whether or not some of them are grounded. the op amp +input itself presents a very high g ? impedance. in the classical noninverting op amp configuration, the lt1996 presents the high input impedance of the op amp, as is usual for the noninverting case. common mode input voltage range the lt1996 valid common mode input range is limited by three factors: 1. maximum allowed voltage on the pins 2. the input voltage range of the internal op amp 3. valid output voltage the maximum voltage allowed on the p27, m27, p81 and m81 inputs includes the positive and negative supply plus a diode drop. these pins should not be driven more than a diode drop outside of the supply rails. this is because they are connected through diodes to internal manufactur- ing post-package trim circuitry, and through a substrate diode to v ee . if more than 10ma is allowed to flow through these pins, there is a risk that the lt1996 will be detrimmed or damaged. the p9 and m9 inputs do not have clamp diodes or substrate diodes or trim circuitry and can be taken well outside the supply rails. the maximum allowed voltage on the p9 and m9 pins is 60v. the input voltage range of the internal op amp extends to within 1.2v of v cc and 1v of v ee . the voltage at which the op amp inputs common mode is determined by the voltage at the op amps +input, and this is determined by the voltages on pins p9, p27, p81 and ref. (see calcu- lating input voltage range section.) this is true provided that the op amp is functioning and feedback is maintaining the inputs at the same voltage, which brings us to the third requirement. for valid circuit function, the op amp output must not be clipped. the output will clip if the input signals are attempt- ing to force it to within 40mv of its supply voltages. this usually happens due to too large a signal level, but it can also occur with zero input differential and must therefore be included as an example of a common mode problem. applicatio s i for atio wu u u lt1996 10 1996f consider figure 1. this shows the lt1996 configured as a gain of 117 difference amplifier on a single supply with figure 3. calculating additional voltage range of inverting inputs these two voltages represent the high and low extremes of the common mode input range, if the other limits have not already been exceeded (1 and 3, above). in most cases, the inverting inputs m9 through m81 can be taken further than these two extremes because doing this does not move the op amp input common mode. to calculate the limit on this additional range, see figure 3. note that, with figure 1. difference amplifier cannot produce 0v on a single supply. provide a negative supply, or raise pin 5, or provide 400 v of v dm the output ref connected to ground. this is a great circuit, but it does not support v dm = 0v at any common mode because the output clips into ground while trying to produce 0v out . it can be fixed simply by declaring the valid input differential range not to extend below +0.4mv, or by elevating the ref pin above 40mv, or by providing a negative supply. calculating input voltage range figure 2 shows the lt1996 in the generalized case of a difference amplifier, with the inputs shorted for the com- mon mode calculation. the values of r f and r g are dictated by how the p inputs and ref pin are connected. by superposition we can write: v int = v ext ? (r f /(r f + r g )) + v ref ? (r g /(r f + r g )) or, solving for v ext : v ext = v int ? (1 + r g /r f ) C v ref ? r g /r f but valid v int voltages are limited to v cc C 1.2v and v ee + 1v, so: max v ext = (v cc C 1.2) ? (1 + r g /r f ) C v ref ? r g /r f and: min v ext = (v ee + 1) ? (1 + r g /r f ) C v ref ? r g /r f figure 2. calculating cm input voltage range v more = 0, the op amp output is at v ref . from the max v ext (the high cm limit), as v more goes positive, the op amp output will go more negative from v ref by the amount v more ? r f /r g , so: v out = v ref C v more ? r f /r g or: v more = (v ref C v out ) ? r g /r f the most negative that v out can go is v ee + 0.04v, so: max v more = (v ref C v ee C 0.04v) ? r g /r f (should be positive) the situation where this function is negative, and therefore problematic, when v ref = 0 and v ee = 0, has already been dealt with in figure 1. the strength of the equation is demonstrated in that it provides the three solutions applicatio s i for atio wu u u 4pf 4pf C + 1996 f01 450k/81 450k/27 450k/9 450k/81 450k/27 450k/9 450k 450k ref 5v v cm 2.5v v dm 0v C + 8 7 6 5 4 9 10 1 2 3 lt1996 v out = 117 ? v dm 4pf 4pf C + v ref r f r f r g r g 1996 f02 v ext v int v cc v ee C + v ref r f r f r g r g 1996 f03 v ext max or min v int v more v cc v ee lt1996 11 1996f representation of the circuit on the top. the lt1996 is shown on the bottom configured in a precision gain of 9.1. one of the benefits of the noninverting op amp configura- tion is that the input impedance is extremely high. the lt1996 maintains this benefit. given the finite number of available feedback resistors in the lt1996, the number of gain configurations is also finite. the complete list of such hi-z input noninverting gain configurations is shown in table 1. many of these are also represented in figure 5 in schematic form. note that the p-side resistor inputs have been connected so as to match the source impedance seen by the internal op amp inputs. note also that gain and noise gain are identical, for optimal precision. table 1. configuring the m pins for simple noninverting gains. the p inputs are driven as shown in the examples on the next page m81, m27, m9 connection gain m81 m27 m9 1 output output output 1.08 output output grounded 1.11 output float grounded 1.30 output grounded output 1.32 float output grounded 1.33 output grounded float 1.44 output grounded grounded 3.19 grounded output output 3.7 float grounded output 3.89 grounded output float 4.21 grounded output grounded 9.1 grounded float output 10 float float grounded 11.8 grounded grounded output 28 float grounded float 37 float grounded grounded 82 grounded float float 91 grounded float grounded 109 grounded grounded float 118 grounded grounded grounded suggested in figure 1: raise v ref , lower v ee , or provide some negative v more . likewise, from the lower common mode extreme, making the negative input more negative will raise the output voltage, limited by v cc C 0.04v. min v more = (v ref C v cc + 0.04v) ? r g /r f (should be negative) again, the additional input range calculated here is only available provided the other remaining constraint is not violated, the maximum voltage allowed on the pin. the classical noninverting amplifier: high input z perhaps the most common op amp configuration is the noninverting amplifier. figure 4 shows the textbook figure 4. the lt1996 as a classical noninverting op amp applicatio s i for atio wu u u 4pf 4pf C + r f r g v in v in v out v out v out = gain ? v in gain = 1 + r f /r g C + 1996 f04 450k/81 450k/27 450k/9 450k/81 450k/27 450k/9 450k 450k 8 6 5 9 10 1 2 3 lt1996 classical noninverting op amp configuration. you provide the resistors. classical noninverting op amp configuration implemented with lt1991. r f = 45k, r g = 5.6k, gain = 9.1. gain is achieved by grounding, floating or feeding back the available resistors to arrive at desired r f and r g . we provide you with <0.1% resistors. 4pf 4pf lt1996 12 1996f figure 5. some implementations of classical noninverting gains using the lt1996. high input z is maintained applicatio s i for atio wu u u v s C v s C v s + 1996 f05 m81 m27 m9 p9 p27 p81 out v cc v out v in v ee v s + v s C v s + v s C v s + v s C v s + v s C v s + v s C v s + v s C v s + v s C v s + v s C v s + v s C v s + ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v in v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v in v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v in v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 v in v in v in out v cc v out v in v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v in v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v in v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v in v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 gain = 1 gain = 10 gain = 3.893 gain = 28 gain = 37 gain = 9.1 gain = 11.8 gain = 82 gain = 109 gain = 118 gain = 91 lt1996 13 1996f figure 6. lt1996 provides for easy attenuation to the op amps +input. the p9 input can be taken well outside of the supplies figure 7. over 600 unique gain settings achievable with the lt1996 by combining attenuation with noninverting gain attenuation using the p input resistors attenuation happens as a matter of fact in difference amplifier configurations, but it is also used for reducing peak signal level or improving input common mode range even in single ended systems. when signal conditioning indicates a need for attenuation, the lt1996 resistors are ready at hand. the four precision resistors can provide several attenuation levels, and these are tabulated in table 2 as a design reference. because the attenuations and the noninverting gains are set independently, they can be combined. this provides high gain resolution, about 700 unique gains between 0.0085 and 118, as plotted in figure 7. this is too large a number to tabulate, but the designer can calculate achiev- able gain by taking the vector product of the gains and attenuations in tables 1 and 2, and seeking the best match. average gain resolution is 1.5%, with worst case steps of about 50% as seen in figure 7. table 2. configuring the p pins for various attenuations. those shown in bold are functional even when the input drive exceeds the supplies p81, p27, p9, ref connection a p81 p27 p9 ref 0.0085 grounded grounded grounded driven 0.0092 grounded grounded float driven 0.0110 grounded float grounded driven 0.0122 grounded float float driven 0.0270 float grounded grounded driven 0.0357 float grounded float driven 0.0763 grounded grounded driven grounded 0.0769 grounded grounded driven float 0.0847 grounded grounded driven driven 0.0989 grounded float driven grounded 0.1 grounded float driven float 0.110 grounded float driven driven 0.229 grounded driven grounded grounded 0.231 grounded driven grounded float 0.237 grounded driven grounded driven 0.243 float grounded driven grounded 0.248 grounded driven float grounded 0.25 float grounded driven float 0.25 grounded driven float float 0.257 grounded driven float driven 0.270 float grounded driven driven 0.305 grounded driven driven grounded 0.308 grounded driven driven float 0.314 grounded driven driven driven 0.686 driven grounded grounded grounded 0.692 driven grounded grounded float 0.695 driven grounded grounded driven 0.730 float driven grounded grounded 0.743 driven grounded float grounded 0.75 float driven grounded float 0.752 driven grounded float driven 0.757 float driven grounded driven 0.763 driven grounded driven grounded 0.769 driven grounded driven float 0.771 driven grounded driven driven 0.890 driven float grounded grounded 0.9 float float driven grounded 0.901 driven float grounded driven 0.915 driven driven grounded grounded 0.923 driven driven grounded float 0.924 driven driven grounded driven 0.964 float driven float grounded 0.973 float driven driven grounded 0.988 driven float float grounded 0.989 driven float driven grounded 0.991 driven driven float grounded 0.992 driven driven driven grounded applicatio s i for atio wu u u v in okay up to 60v + 450k/81 450k/27 450k/9 450k 5 1 2 3 lt1991 attenuating to the +input by driving and grounding and floating inputs r a = 50k, r g = 50k/9, so a = 0.1. v int v int v int = a ? v in a = r g /(r a + r g ) v in lt1996 r a r g 1996 f06 classical attenuator count 0 1000 100 10 1 0.1 0.01 0.001 300 1996 f07 100 200 400 500 700 600 gain lt1996 14 1996f table 3. configuring the m pins for simple inverting gains m81, m27, m9 connection gain m81 m27 m9 C0.083 output output drive C0.110 output float drive C0.297 output drive output C0.321 float output drive C0.329 output drive float C0.439 output drive drive C2.19 drive output output C2.7 float drive output C2.89 drive output float C3.21 drive output drive C8.1 drive float output C9 float float drive C10.8 drive drive output C27 float drive float C36 float drive drive C81 drive float float C90 drive float drive C108 drive drive float C117 drive drive drive inverting configuration the inverting amplifier, shown in figure 8, is another classical op amp configuration. the circuit is actually identical to the noninverting amplifier of figure 4, except that v in and gnd have been swapped. the list of available gains is shown in table 3, and some of the circuits are shown in figure 9. noise gain is 1+|gain|, as is the usual case for inverting amplifiers. again, for the best dc perfor- mance, match the source impedance seen by the op amp inputs. 4pf 4pf C + r f r g v in v in (drive) v out v out v out = gain ? v in gain = C r f /r g C + 1996 f08 450k 450k 8 6 5 9 10 1 2 3 lt1996 classical inverting op amp configuration. you provide the resistors. classical inverting op amp configuration implemented with lt1991. r f = 45k, r g = 5.55k, gain = C8.1. gain is achieved by grounding, floating or feeding back the available resistors to arrive at desired r f and r g . we provide you with <0.1% resistors. 450k/81 450k/27 450k/9 450k/81 450k/27 450k/9 4pf 4pf figure 8. the lt1996 as a classical inverting op amp. note the circuit is identical to the noninverting amplifier, except that v in and ground have been swapped applicatio s i for atio wu u u lt1996 15 1996f 4 v s C 4 v s C v s + 1996 f09 m81 m27 m9 p9 p27 p81 out v cc v out v in v ee v s C v s + v s C v s + v s + v s C v s + v s C v s + v s C v s + v s C v s + v s C v s + v s C v s + v s C v s + ref lt1996 8 9 10 1 2 3 7 6 5 m81 m27 m9 p9 p27 p81 out v cc v out v in v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v in v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v in v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 v in v in v in out v cc v out v in v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v in v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v in v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 m81 m27 m9 p9 p27 p81 out v cc v out v in v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 gain = C0.321 gain = C9 gain = C2.89 gain = C27 gain = C36 gain = C8.1 gain = C10.8 gain = C81 gain = C108 gain = C117 gain = C90 figure 9. it is simple to get precision inverting gains with the lt1996. input impedance varies from 3.8k ? (gain = C117) to 50k ? (gain = C9) applicatio s i for atio wu u u lt1996 16 1996f figure 10. difference amplifier using the lt1996. gain is set simply by connecting the correct resistors or combinations of resistors. gain of 27 is shown, with dashed lines modifying it to gain of 2.7. noise gain is optimal difference amplifiers the resistors in the lt1996 allow it to easily make differ- ence amplifiers also. figure 10 shows the basic 4-resistor difference amplifier and the lt1996. a difference gain of 27 is shown, but notice the effect of the additional dashed connections. by connecting the 50k resistors in parallel, the gain is reduced by a factor of 10. of course, with so many resistors, there are many possible gains. table 4 shows the difference gains and how they are achieved. note that, as for inverting amplifiers, the noise gain is 1 more than the signal gain. table 4. connections giving difference gains for the lt1996 gain v in + v in C output gnd (ref) 0.083 p9 m9 m27, m81 p27, p81 0.110 p9 m9 m81 p81 0.297 p27 m27 m9, m81 p9, p81 0.321 p9 m9 m27 p27 0.329 p27 m27 m81 p81 0.439 p9, p27 m9, m27 m81 p81 2.189 p81 m81 m9, m27 p9, p27 2.700 p27 m27 m9 p9 2.893 p81 m81 m27 p27 3.214 p9, p81 m9, m81 m27 p27 8.1 p81 m81 m9 p9 9 p9 m9 10.8 p27, p81 m27, m81 m9 p9 27 p27 m27 36 p9, p27 m9, m27 81 p81 m81 90 p9, p81 m9, m81 108 p27, p81 m27, m81 117 p9, p27, p81 m9, m27, m81 applicatio s i for atio wu u u 4pf 4pf C + r f r g r g v in + v in + v in C v in C v out v out v out = gain ? (v in + C v in C ) gain = r f /r g C + 1996 f10 450k 450k 8 6 5 9 10 1 2 3 lt1996 classical difference amplifier using the lt1991 classical difference amplifier implemented with lt1991. r f = 450k, r g = 16.7k, gain = 3. adding the dashed connections connects the two 450k resistor in parallel, so r f is reduced to 45k. gain becomes 45k/16.7k = 2.7. r f parallel to change r f , r g 450k/81 450k/27 450k/9 450k/81 450k/27 450k/9 4pf 4pf lt1996 17 1996f figure 11. many difference gains are achievable just by strapping the pins applicatio s i for atio wu u u v s C v s + 1996 f11 m81 m27 m9 p9 p27 p81 out v cc v out v ee v s C v s + v s C v s + v s C v s + v s C v s + v s C v s + v s C v s + v s C v s + v s C v s + v s C v s + v s C v s + ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 gain = 0.321 gain = 9 gain = 2.89 gain = 27 gain = 36 gain = 8.1 gain = 10.8 gain = 81 gain = 108 gain = 117 gain = 90 v in + v in C v in + v in + v in + v in C v in + v in C v in + v in C v in + v in C v in + v in C v in + v in C v in + v in C v in + v in C v in C v in C lt1996 18 1996f difference amplifier: additional integer gains using cross-coupling figure 12 shows the basic difference amplifier as well as the lt1996 in a difference gain of 27. but notice the effect of the additional dashed connections. this is referred to as cross-coupling and has the effect of reducing the differ- ential gain from 27 to 18. using this method, additional integer gains are achievable, as shown in table 5 below. note that the equations can be written by inspection from the v in + connections, and that the v in C connections are simply the opposite (swap p for m and m for p). the method is the same as for the lt1991, except that the lt1996 applies a multiplier of 9. noise gain, bandwidth, and input impedance specifications for the various cases are also tabulated, as these are not obvious. schematics are provided in figure 13. table 5. connections using cross-coupling. note that equations can be written by inspection of the v in + column gain noise C3db bw r in + r in C gain v in + v in C equation gain khz typ k ? typ k ? 18 p27, m9 m27, p9 27 C 9 39 14 46 16 45 p81, m27, m9 m81, p27, p9 81 C 27 C 9 117 5 12 6 54 p81, m27 m81, p27 81 C 27 108 5 16 6 63 p81, p9, m27 m81, m9, p27 81 + 9 C 27 117 5 16 5 72 p81, m9 m81, p9 81 C 9 90 6 45 6 99 p81, p27, m9 m81, m27, p9 81 + 27 C 9 117 5 45 4 figure 12. another method of selecting difference gain is cross-coupling. the additional method means the lt1996 provides extra integer gains figure 13. integer gain difference amplifiers using cross-coupling applicatio s i for atio wu u u 1996 f13 v s C v s + v s C v s + v s C v s + v s C v s + m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 gain = 18 gain = 54 gain = 63 gain = 72 gain = 99 v in + v in C v s C v s + m81 m27 m9 p9 p27 p81 out v cc v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 gain = 45 v in + v in C v in + v in C v in + v in C v in + v in C v s C v s + m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 v in + v in C 4pf 4pf C + r f r g r g v in + v in + v in C v in C v out v out v out = gain ? (v in + C v in C ) gain = r f /r g C + 1996 f10 450k 450k 8 6 5 9 10 1 2 3 lt1996 classical difference amplifier classical difference amplifier implemented with lt1991. r f = 450k, r g = 16.7k, gain = 27. gain can be adjusted by "cross coupling." making the dashed connections reduce the gain from 3 t0 2. when cross coupling, see what is connected to the v in + voltage. connecting p27 and m9 gives 27 C 9 = 18. connections to v in C are symmetric: m27 and p9. r f cross- coupling 450k/81 450k/27 450k/9 450k/81 450k/27 450k/9 4pf 4pf lt1996 19 1996f high voltage cm difference amplifiers this class of difference amplifier remains to be discussed. figure 14 shows the basic circuit on the top. the effective input voltage range of the circuit is extended by the fact that resistors r t attenuate the common mode voltage seen by the op amp inputs. for the lt1996, the most useful resistors for r g are the m9 and p9 50k ? resistors, because they do not have diode clamps to the supplies and therefore can be taken outside the supplies. as before, the input cm of the op amp is the limiting factor and is set by the voltage at the op amp +input, v int . by superposition we can write: v int = v ext ? (r f ||r t )/(r g + r f ||r t ) + v ref ? (r g ||r t )/ (r f + r g ||r t ) + v term ? (r f ||r g )/(r t + r f ||r g ) solving for v ext : v ext = (1 + r g /(r f ||r t )) ? (v int C v ref ? (r g ||r t )/ (r f + r g ||r t ) C v term ? (r f ||r g )/(r t + r f ||r g )) given the values of the resistors in the lt1996, this equation has been simplified and evaluated, and the re- sulting equations provided in table 6. as before, substi- tuting v cc C 1.2 and v ee + 1 for v lim will give the valid upper and lower common mode extremes respectively. following are sample calculations for the case shown in figure 14, right-hand side. note that p81 and m81 are terminated so row 3 of table 6 provides the equation: max v ext = 91/9 ? (v cc C 1.2v) C v ref /9 C 9 ? v term = (10.11) ? (10.8) C 0.11(2.5) C 9(10) = 18.9v and: min v ext = 91/9 ? (v ee + 1v) C v ref /9 C 9 ? v term = (10.11)(1) C 0.11(2.5) C 9(10) = C80.2v but this exceeds the 60v absolute maximum rating of the p9, m9 pins, so C60v becomes the de facto negative common mode limit. several more examples of high cm circuits are shown in figures 15, 16, 17 for various supplies. figure 14. extending cm input range 4pf 4pf C + r f r g r g v in + (= v ext ) v in + v in C v in C v out v out v out = gain ? (v in + C v in C ) gain = r f /r g C + 1996 f14 450k 450k 8 7 4 6 5 9 10 1 2 3 lt1996 ref high cm voltage difference amplifier input cm to op amp is attenuated by resistors r t connected to v term. high negative cm voltage difference amplifier implemented with lt1996. r f = 450k, r g = 50k, r t 5.55k, gain = 9 v term = 10v = v cc = 12v, v ref = 2.5v, v ee = 0v. r f v cc v ee r t r t v term v ref input cm range = C60v to 18.9v 10v 12v 2.5v 450k/81 450k/27 450k/9 450k/81 450k/27 450k/9 4pf 4pf table 6. highv cm connections giving difference gains for the lt1996 max, min v ext noise (substitute v cc C 1.2, gain v in + v in C r t gain v ee + 1 for v lim ) 9 p9 m9 10 10/9 ? v lim - v ref /9 9 p9 m9 p27, m27 37 37/9 ? v lim C v ref /9 C 3 ? v term 9 p9 m9 p81, m81 91 91/9 ? v lim C v ref /9 C 9 ? v term 9 p9 m9 p27||p81 118 118/9 ? v lim C v ref /9 C 12 ? v term m27||m81 applicatio s i for atio wu u u lt1996 20 1996f 3v 1996 f15 m81 m27 m9 p9 p27 p81 out v cc v out v in C v in + v in C v in + v in C v in + v in C v in + v ee 3v 3v 3v 3v ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 out v cc v out v ee ref lt1996 8 9 10 1 2 3 7 6 5 4 v cm = 0.97v to 1.86v v cm = 0.22v to 3.5v v cm = 1.11v to 2v v dm > 45mv v cm = C.78v to 1.67v v dm lt1996 24 1996f part number description comments lt1990 high voltage difference amplifier 250v input common mode, micropower, pin selectable gain = 1, 10 lt1991 precision, 100 a gain selectable amplifier gain resistors of 450k, 150k, 50k lt1995 30mhz, 1000v/ s gain selectable amplifier high speed, pin selectable gain = C7 to 8 lt6010/lt6011/lt6012 single/dual/quad precision op amp similar performance as lt1996 diff amp, 135 a, 14nv hz, rail-to-rail out lt6013/lt6014 single/dual precision op amp lower noise a v 5 version of lt1991, 145 a, 8nv/ hz, rail-to-rail out ltc6910-x programmable gain amplifiers 3 gain configurations, rail-to-rail input and output linear technology corporation 1630 mccarthy blvd., milpitas, ca 95035-7417 (408) 432-1900 fax: (408) 434-0507 www.linear.com ? linear technology corporation 2005 lt/tp 0205 1k ? printed in usa related parts typical applicatio u C + C + v m v p v out lt1996 1996 ta02 98 23 4 5 7 6 10 1 C + 1/2 lt6011 1/2 lt6011 450k/81 450k/27 450k/9 450k/9 450k/27 450k/81 450k 450k 4pf 4pf micropower a v = 90 instrumentation amplifier v in C v in + v in v s + v s C v s + v s C m81 m27 m9 p9 p27 p81 lt1996 8 9 10 1 2 3 7 6 5 4 m81 m27 m9 p9 p27 p81 v out lt1996 8 9 10 1 2 3 7 6 5 4 gain = 117 bw = 4hz to 5khz r1 10k 9( v in + C v in C ) 10k ? i load = 0.1 f 1996 ta03 v in C v in + v out C v out + v ocm v s + v s C m81 m27 m9 p9 p27 p81 lt1996 8 9 10 1 2 3 7 6 5 4 10k 10k use v ocm to set the desired output common mode level C + lt6010 bidirectional controlled current source ac coupled amplifier differential input/output g = 9 amplifier |
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